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High Voltage Switching Regulator
The MC33363A is a monolithic high voltage switching regulator that is specifically designed to operate from a rectified 240 Vac line source. This integrated circuit features an on-chip 700 V/1.5 A SenseFET power switch, 500 V active off-line startup FET, duty cycle controlled oscillator, current limiting comparator with a programmable threshold and leading edge blanking, latching pulse width modulator for double pulse suppression, high gain error amplifier, and a trimmed internal bandgap reference. Protective features include cycle-by-cycle current limiting, input undervoltage lockout with hysteresis, output overvoltage protection, and thermal shutdown. This device is available in a 16-lead dual-in-line and wide body surface mount packages. * Enhanced Power Capability Over MC33363
MC33363A
HIGH VOLTAGE OFF-LINE SWITCHING REGULATOR
SEMICONDUCTOR TECHNICAL DATA
16 1
* * * * * * * * *
On-Chip 700 V, 1.5 A SenseFET Power Switch Rectified 240 Vac Line Source Operation On-Chip 500 V Active Off-Line Startup FET Latching PWM for Double Pulse Suppression Cycle-By-Cycle Current Limiting Input Undervoltage Lockout with Hysteresis Output Overvoltage Protection Comparator Trimmed Internal Bandgap Reference Internal Thermal Shutdown
16 1
DW SUFFIX PLASTIC PACKAGE CASE 751N (SOP-16L)
Simplified Application
P SUFFIX PLASTIC PACKAGE CASE 648E (DIP-16)
AC Input Startup Input Regulator Output 8 6 RT CT Osc 7 PWM Latch S Q PWM R Ipk Thermal LEB Compensation 9 EA 10 Voltage Feedback Input Driver OVP Startup Reg UVLO VCC 3 Overvoltage Protection Input 11 16 Power Switch Drain DC Output 1
PIN CONNECTIONS
Startup Input 1 16 Power Switch Drain
Mirror
VCC Gnd
3 4 5 13 Gnd 12 11 10 9 (Top View) Overvoltage Protection Input Voltage Feedback Input Compensation 6 7 8
RT CT Regulator Output
ORDERING INFORMATION
Device MC33363ADW Operating Temperature Range TJ = -25 to +125C Package SOP-16L DIP-16
Rev 1
Gnd
4, 5, 12, 13
This device contains 221 active transistors.
MC33363AP
(c) Motorola, Inc. 1998
MOTOROLA ANALOG IC DEVICE DATA
1
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ELECTRICAL CHARACTERISTICS (VCC = 20 V, RT = 10 k, CT = 390 pF, CPin 8 = 1.0 F, for typical values TJ = 25C, for min/max values TJ is the operating junction temperature range that applies (Note 2), unless otherwise noted.)
NOTES: 1. Maximum power dissipation limits must be observed. 2. Tested junction temperature range for the MC33363A: Tlow = -25C Thigh = +125C
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MAXIMUM RATINGS
NOTE:
ERROR AMPLIFIER (Pins 9, 10)
OSCILLATOR (Pin 7)
REGULATOR (Pin 8)
2
Thermal Characteristics P Suffix, Dual-In-Line Case 648E Thermal Resistance, Junction-to-Air Thermal Resistance, Junction-to-Case (Pins 4, 5, 12, 13) DW Suffix, Surface Mount Case 751N Thermal Resistance, Junction-to-Air Thermal Resistance, Junction-to-Case (Pins 4, 5, 12, 13) Refer to Figures 15 and 16 for additional thermal information. Gain Bandwidth Product (f = 100 kHz, TJ = 25C) Open Loop Voltage Gain (TJ = 25C) Input Bias Current (VFB = 2.6 V) Line Regulation (VCC = 20 V to 40 V, TJ = 25C) Voltage Feedback Input Threshold Frequency Change with Voltage (VCC = 20 V to 40 V) Frequency CT = 390 pF TJ = 25C (VCC = 20 V) TJ = Tlow to Thigh (VCC = 20 V to 40 V) CT = 2.0 nF TJ = 25C (VCC = 20 V) TJ = Tlow to Thigh (VCC = 20 V to 40 V) Total Output Variation over Line, Load, and Temperature Load Regulation (IO = 0 mA to 10 mA) Line Regulation (VCC = 20 V to 40 V) Output Voltage (IO = 0 mA, TJ = 25C) Storage Temperature Operating Junction Temperature Input Voltage Range Voltage Feedback Input (Pin 10) Compensation (Pin 9) Overvoltage Protection Input (Pin 11) RT (Pin 6) CT (Pin 7) Power Supply Voltage (Pin 3) Startup Input Voltage (Pin 1, Note 1) Pin 3 = Gnd Pin 3 1000 F to ground Power Switch (Pin 16) Drain Voltage Drain Current
ESD data available upon request.
Rating
Characteristic
Symbol
RJA RJC
RJA RJC
VCC
VDS IDS
Tstg
VIR
Vin
TJ
MC33363A
-1.0 to Vreg
-55 to +150
-25 to +150
Value
400 500
700 1.5
95 15
80 15
40
fOSC/V
Regload
Symbol
Regline
Regline
AVOL
fOSC
GBW
Vreg
Vreg
VFB
IIB
C/W
Unit
C
C
V
V
V
V A
MOTOROLA ANALOG IC DEVICE DATA
2.52 Min 260 255 5.3 5.5 60 59 - - - - - - - 67.5 - Typ 285 - 1.0 0.6 2.6 0.1 6.5 82 20 44 30 - 2.68 Max 500 310 315 200 500 5.0 2.0 8.0 7.5 75 76 - - MHz Unit kHz kHz mV mV mV dB nA V V V
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ELECTRICAL CHARACTERISTICS (continued) (VCC = 20 V, RT = 10 k, CT = 390 pF, CPin 8 = 1.0 F, for typical values TJ = 25C, for min/max values TJ is the operating junction temperature range that applies (Note 2), unless otherwise noted.)
TOTAL DEVICE (Pin 3) UNDERVOLTAGE LOCKOUT (Pin 3) STARTUP CONTROL (Pin 1) OVERCURRENT COMPARATOR (Pin 16) POWER SWITCH (Pin 16) PWM COMPARATOR (Pins 7, 9) OVERVOLTAGE DETECTION (Pin 11) ERROR AMPLIFIER (Pins 9, 10) Power Supply Current Startup (VCC = 10 V, Pin 1 Open) Operating Minimum Operating Voltage After Turn-On Startup Threshold (VCC Increasing) Off-State Leakage Current (Vin = 50 V, VCC = 20 V) Peak Startup Current (Vin = 400 V) VCC = 0 V VCC = (Vth(on) - 0.2 V) Current Limit Threshold (RT = 13 k) Fall Time Rise Time Drain-Source Off-State Leakage Current TJ = 25C to 125C, VDS = 700 V TJ = -25C, VDS = 650 V Drain-Source On-State Resistance (ID = 200 mA) TJ = 25C TJ = Tlow to Thigh Duty Cycle Maximum (VFB = 0 V) Minimum (VFB = 2.7 V) Input Bias Current (Vin = 2.6 V) Input Threshold Voltage Output Voltage Swing High State (ISource = 100 A, VFB < 2.0 V) Low State (ISink = 100 A, VFB > 3.0 V) Characteristic
MOTOROLA ANALOG IC DEVICE DATA
f OSC , OSCILLATOR FREQUENCY (Hz)
Figure 1. Oscillator Frequency versus Timing Resistor
I PK, POWER SWITCH PEAK DRAIN CURRENT (A)
1.0 M
100 k CT = 1.0 nF
200 k CT = 500 pF
500 k C = 200 pF T
10 k 7.0
C = 5.0 nF 20 k T
C = 2.0 nF 50 k T
CT = 10 nF
CT = 100 pF
10
RT, TIMING RESISTOR (k) 15 20 30 VCC = 20 V TA = 25C 50
MC33363A
70
0.15 7.0
VCC(min)
DC(max) DC(min)
RDS(on)
0.2
0.3
0.4
0.6
1.0 0.8
1.5
Symbol
Vth(on)
ID(off)
ID(off)
Istart
VOH VOL
ICC
Ilim
Vth
IIB
tr
tf
Inductor supply voltage and inductance value are adjusted so that Ipk turn-off is achieved at 5.0 s.
Figure 2. Power Switch Peak Drain Current versus Timing Resistor
10
2.47
Min
7.5
0.7
4.0 -
48 -
11
- -
-
- -
-
-
- -
- -
-
RT, TIMING RESISTOR (k) 15 20 0.27 3.4 14.9 Typ 100 22 6.0 9.5 0.9 0.2 0.2 7.5 - 2.6 5.3 0.2 40 50 50 50 0 30 2.73 - 0.35 Max 11.5 200 100 100 500 0.5 5.0 1.1 9.0 20 18 52 0 - - - - 40 VCC = 20 V CT = 1.0 F TA = 25C 50 Unit mA mA A A nA ns ns % V V A V V 70
3
MC33363A
Figure 3. Oscillator Charge/Discharge Current versus Timing Resistor
Dmax, MAXIMUM OUTPUT DUTY CYCLE (%) 0.8 I chg /I dscg , OSCILLATOR CHARGE/DISCHARGE CURRENT (mA) VCC = 20 V TA = 25C 70
Figure 4. Maximum Output Duty Cycle versus Timing Resistor Ratio
RD/RT Ratio Discharge Resistor Pin 6 to Gnd VCC = 20 V CT = 2.0 nF TA = 25C
0.5
60
0.3 0.2 0.15 0.1 0.08 7.0 10 15 20 30 50 70
50
40
30 1.0
RC/RT Ratio Charge Resistor Pin 6 to Vreg 2.0 3.0 5.0 7.0 10 TIMING RESISTOR RATIO
RT, TIMING RESISTOR (k)
Figure 5. Error Amp Open Loop Gain and Phase versus Frequency
, EXCESS PHASE (DEGREES) VCC = 20 V VO = 1.0 to 4.0 V RL = 5.0 M CL = 2.0 pF TA = 25C Vsat , OUTPUT SATURATION VOLTAGE (V) A VOL, OPEN LOOP VOLTAGE GAIN (dB) 100 80 Gain 60 Phase 40 20 0 -20 10 90 120 150 180 10 M 0 30 60 0 -1.0 - 2.0
Figure 6. Error Amp Output Saturation Voltage versus Load Current
Source Saturation (Load to Ground) Vref
2.0 1.0 0
Sink Saturation (Load to Vref) Gnd 0 0.2 0.4 0.6
VCC = 20 V TA = 25C
100
1.0 k
10 k
100 k
1.0 M
0.8
1.0
f, FREQUENCY (Hz)
IO, OUTPUT LOAD CURRENT (mA)
Figure 7. Error Amplifier Small Signal Transient Response
VCC = 20 V AV = -1.0 CL = 10 pF TA = 25C 20 mV/DIV
Figure 8. Error Amplifier Large Signal Transient Response
VCC = 20 V AV = -1.0 CL = 10 pF TA = 25C 0.5 V/DIV 1.0 s/DIV
1.80 V
3.00 V
1.75 V
1.75 V
1.70 V
0.50 V
1.0 s/DIV
4
MOTOROLA ANALOG IC DEVICE DATA
MC33363A
V reg, REGULATOR VOLTAGE CHANGE (mV)
Figure 9. Regulator Output Voltage Change versus Source Current
0 I pk , PEAK STARTUP CURRENT (mA) VCC = 20 V RT = 10 k TA = 25C 24
Figure 10. Peak Startup Current versus Power Supply Voltage
VPin 1 = 400 V TA = 25C
-20
-40
12
-60
Pulse tested with an on-time of 20 s to 300 s at < 1.0% duty cycle. The on-time is adjusted at Pin 1 for a maximum peak current out of Pin 3. 0 0 2.0 4.0 6.0 8.0 10 12 14
-80
0
4.0
8.0
12
16
20
Ireg, REGULATOR SOURCE CURRENT (mA)
VCC, POWER SUPPLY VOLTAGE (V)
R DS(on), DRAIN-SOURCE ON-RESISTANCE ( )
Figure 11. Power Switch Drain-Source On-Resistance versus Temperature
COSS, DRAIN-SOURCE CAPACITANCE (pF) 32 ID = 200 mA 24 160
Figure 12. Power Switch Drain-Source Capacitance versus Voltage
VCC = 20 V TA = 25C 120
16 8.0 4.0 0 -50
80
40 COSS measured at 1.0 MHz with 50 mVpp. 10 100 1000 VDS, DRAIN-SOURCE VOLTAGE (V)
Pulse tested at 5.0 ms with < 1.0% duty cycle so that TJ is as close to TA as possible. -25 0 25 50 75 100 125 150
0 1.0
TA, AMBIENT TEMPERATURE (C)
Figure 13. Supply Current versus Supply Voltage
3.6 I CC, SUPPLY CURRENT (mA) 3.2 2.4 1.6 0.8 RT = 10 k Pin 1 = Open Pin 4, 5, 10, 11, 12, 13 = Gnd TA = 25C 0 10 20 VCC, SUPPLY VOLTAGE (V) 30 40 CT = 390 pF CT = 2.0 nF 100 R JA , THERMAL RESISTANCE JUNCTION-TO-AIR (C/W)
Figure 14. DW and P Suffix Transient Thermal Resistance
L = 12.7 mm of 2.0 oz. copper. Refer to Figures 15 and 16.
10
0
1.0 0.01
0.1
1.0 t, TIME (s)
10
100
MOTOROLA ANALOG IC DEVICE DATA
5
MC33363A
Figure 15. DW Suffix (SOP-16L) Thermal Resistance and Maximum Power Dissipation versus P.C.B. Copper Length
PD, MAXIMUM POWER DISSIPATION (W) 100 R JA , THERMAL RESISTANCE JUNCTION-TO-AIR (C/W) 90 80 70 60 50 RJA 40 30 0 10 20 PD(max) for TA = 50C 2.8 2.4 2.0 1.6 1.2 0.8 0.4
Figure 16. P Suffix (DIP-16) Thermal Resistance and Maximum Power Dissipation versus P.C.B. Copper Length
Printed circuit board heatsink example
80 60 40 20 PD(max) for TA = 70C RJA
L
2.0 oz Copper
4.0 3.0 2.0 1.0 0 50
L, LENGTH OF COPPER (mm)
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Pin 1
Function
Startup Input
2 3
-
VCC
4, 5, 12, 13 6 7 8 9
Ground RT
CT
Regulator Output Compensation
10
Voltage Feedback Input Overvoltage Protection Input
11
14, 15 16
-
Power Switch Drain
6
IIIIII IIIIII IIIIII
L 2.0 oz Copper L 3.0 mm Graphs represent symmetrical layout
Printed circuit board heatsink example
L 3.0 mm Graphs represent symmetrical layout
30
40
0 50
0
0
10
20
30
40
L, LENGTH OF COPPER (mm)
PIN FUNCTION DESCRIPTION
Description
This pin connects directly to the rectified ac line voltage source. Internally Pin 1 is tied to the drain of a high voltage startup MOSFET. During startup, the MOSFET supplies internal bias, and charges an external capacitor that connects from the VCC pin to ground. This pin has been omitted for increased spacing between the rectified ac line voltage on Pin 1 and the VCC potential on Pin 3.
This is the positive supply voltage input. During startup, power is supplied to this input from Pin 1. When VCC reaches the UVLO upper threshold, the startup MOSFET turns off and power is supplied from an auxiliary transformer winding. These pins are the control circuit grounds. They are part of the IC lead frame and provide a thermal path from the die to the printed circuit board. Resistor RT connects from this pin to ground. The value selected will program the Current Limit Comparator threshold and affect the Oscillator frequency.
Capacitor CT connects from this pin to ground. The value selected, in conjunction with resistor RT, programs the Oscillator frequency. This 6.5 V output is available for biasing external circuitry. It requires an external bypass capacitor of at least 1.0 F for stability.
This pin is the Error Amplifier output and is made available for loop compensation. It can be used as an input to directly control the PWM Comparator. This is the inverting input of the Error Amplifier. It has a 2.6 V threshold and normally connects through a resistor divider to the converter output, or to a voltage that represents the converter output.
This input provides runaway output voltage protection due to an external component or connection failure in the control loop feedback signal path. It has a 2.6 V threshold and normally connects through a resistor divider to the converter output, or to a voltage that represents the converter output. These pins have been omitted for increased spacing between the high voltages present on the Power Switch Drain, and the ground potential on Pins 12 and 13. This pin is designed to directly drive the converter transformer and is capable of switching a maximum of 700 V and 1.0 A.
MOTOROLA ANALOG IC DEVICE DATA
P D , MAXIMUM POWER DISSIPATION (W)
100 R JA, THERMAL RESISTANCE JUNCTION-TO-AIR (C/W)
5.0
III I IIIII III
MC33363A
Figure 17. Representative Block Diagram
AC Input Startup Input Current Mirror Startup Control Band Gap Regulator 2.25 I UVLO 14.5 V/ 9.5 V OVP PWM Latch S Q PWM Comparator R Leading Edge Blanking 6.0 Current Limit Comparator Compensation 450 2.6 V 10 Voltage Feedback Input 9 Error Amplifier Driver 2.6 V 16 Power Switch Drain 1
Regulator Output 6.5 V 8 I 6 RT
VCC 3 Overvoltage Protection Input 11 DC Output
4I Oscillator 7
CT
Thermal Shutdown
270 A Gnd 4, 5, 12, 13
Figure 18. Timing Diagram
Capacitor CT Compensation Oscillator Output PWM Comparator Output PWM Latch Q Output Power Switch Gate Drive Leading Edge Blanking Input (Power Switch Drain Current) Normal PWM Operating Range Output Overload
2.6 V 0.6 V
Current Limit Propagation Delay Current Limit Threshold
MOTOROLA ANALOG IC DEVICE DATA
7
MC33363A
OPERATING DESCRIPTION
Introduction The MC33363A represents a new higher level of integration by providing all the active high voltage power, control, and protection circuitry required for implementation of a flyback or forward converter on a single monolithic chip. This device is designed for direct operation from a rectified 240 Vac line source and requires a minimum number of external components to implement a complete converter. A description of each of the functional blocks is given below, and the representative block and timing diagrams are shown in Figures 17 and 18. Oscillator and Current Mirror The oscillator frequency is controlled by the values selected for the timing components RT and CT. Resistor RT programs the oscillator charge/discharge current via the Current Mirror 4 I output, Figure 3. Capacitor CT is charged and discharged by an equal magnitude internal current source and sink. This generates a symmetrical 50 percent duty cycle waveform at Pin 7, with a peak and valley threshold of 2.6 V and 0.6 V respectively. During the discharge of CT, the oscillator generates an internal blanking pulse that holds the inverting input of the AND gate Driver high. This causes the Power Switch gate drive to be held in a low state, thus producing a well controlled amount of output deadtime. The amount of deadtime is relatively constant with respect to the oscillator frequency when operating below 1.0 MHz. The maximum Power Switch duty cycle at Pin 16 can be modified from the internal 50% limit by providing an additional charge or discharge current path to CT, Figure 19. In order to increase the maximum duty cycle, a discharge current resistor RD is connected from Pin 7 to ground. To decrease the maximum duty cycle, a charge current resistor RC is connected from Pin 7 to the Regulator Output. Figure 4 shows an obtainable range of maximum output duty cycle versus the ratio of either RC or RD with respect to RT. The formula for the charge/discharge current along with the oscillator frequency are given below. The frequency formula is a first order approximation and is accurate for CT values greater than 500 pF. For smaller values of CT, refer to Figure 1. Note that resistor RT also programs the Current Limit Comparator threshold. I
I
+ 5.4 R chg dscg T
f
[
chg dscg 4C T
PWM Comparator and Latch The pulse width modulator consists of a comparator with the oscillator ramp voltage applied to the non-inverting input, while the error amplifier output is applied into the inverting input. The Oscillator applies a set pulse to the PWM Latch while CT is discharging, and upon reaching the valley voltage, Power Switch conduction is initiated. When CT charges to a voltage that exceeds the error amplifier output, the PWM Latch is reset, thus terminating Power Switch conduction for the duration of the oscillator ramp-up period. This PWM Comparator/Latch combination prevents multiple output pulses during a given oscillator clock cycle. The timing diagram shown in Figure 18 illustrates the Power Switch duty cycle behavior versus the Compensation voltage. Current Limit Comparator and Power Switch The MC33363A uses cycle-by-cycle current limiting as a means of protecting the output switch transistor from overstress. Each on-cycle is treated as a separate situation. Current limiting is implemented by monitoring the output switch current buildup during conduction, and upon sensing an overcurrent condition, immediately turning off the switch for the duration of the oscillator ramp-up period. The Power Switch is constructed as a SenseFET allowing a virtually lossless method of monitoring the drain current. It consists of a total of 2819 cells, of which 65 are connected to a 6.0 ground-referenced sense resistor. The Current Sense Comparator detects if the voltage across the sense resistor exceeds the reference level that is present at the inverting input. If exceeded, the comparator quickly resets the PWM Latch, thus protecting the Power Switch. The current limit reference level is generated by the 2.25 I output of the Current Mirror. This current causes a reference voltage to appear across the 450 resistor. This voltage level, as well as the Oscillator charge/discharge current are both set by resistor RT. Therefore when selecting the values for RT and CT, RT must be chosen first to set the Power Switch peak drain current, while CT is chosen second to set the desired Oscillator frequency. A graph of the Power Switch peak drain current versus RT is shown in Figure 2 with the related formula below.
Figure 19. Maximum Duty Cycle Modification
Regulator Output 1.0 8 I RC RT 6
Current Mirror 2.25 I Current Limit Reference 4I
RD
CT
7
Oscillator
Blanking Pulse
PWM Comparator
I
+ 15.95 pk
T - 1.14 1000
R
8
MOTOROLA ANALOG IC DEVICE DATA
MC33363A
The Power Switch is designed to directly drive the converter transformer and is capable of switching a maximum of 700 V and 1.0 A. Proper device voltage snubbing and heatsinking are required for reliable operation. A Leading Edge Blanking circuit was placed in the current sensing signal path. This circuit prevents a premature reset of the PWM Latch. The premature reset is generated each time the Power Switch is driven into conduction. It appears as a narrow voltage spike across the current sense resistor, and is due to the MOSFET gate to source capacitance, transformer interwinding capacitance, and output rectifier recovery time. The Leading Edge Blanking circuit has a dynamic behavior in that it masks the current signal until the Power Switch turn-on transition is completed. The current limit propagation delay time is typically 300 ns. This time is measured from when an overcurrent appears at the Power Switch drain, to the beginning of turn-off. Error Amplifier An fully compensated Error Amplifier with access to the inverting input and output is provided for primary side voltage sensing, Figure 17. It features a typical dc voltage gain of 82 dB, and a unity gain bandwidth of 1.0 MHz with 78 degrees of phase margin, Figure 5. The noninverting input is internally biased at 2.6 V 3.1% and is not pinned out. The Error Amplifier output is pinned out for external loop compensation and as a means for directly driving the PWM Comparator. The output was designed with a limited sink current capability of 270 A, allowing it to be easily overridden with a pull-up resistor. This is desirable in applications that require secondary side voltage sensing, Figure 20. In this application, the Voltage Feedback Input is connected to the Regulator Output. This disables the Error Amplifier by placing its output into the sink state, allowing the optocoupler transistor to directly control the PWM Comparator. Overvoltage Protection An Overvoltage Protection Comparator is included to eliminate the possibility of runaway output voltage. This condition can occur if the control loop feedback signal path is broken due to an external component or connection failure. The comparator is normally used to monitor the primary side VCC voltage. When the 2.6 V threshold is exceeded, it will immediately turn off the Power Switch, and protect the load from a severe overvoltage condition. This input can also be driven from external circuitry to inhibit converter operation. Undervoltage Lockout An Undervoltage Lockout comparator has been incorporated to guarantee that the integrated circuit has sufficient voltage to be fully functional before the output stage is enabled. The UVLO comparator monitors the VCC voltage at Pin 3 and when it exceeds 14.5 V, the reset signal is removed from the PWM Latch allowing operation of the Power Switch. To prevent erratic switching as the threshold is crossed, 5.0 V of hysteresis is provided. Startup Control An internal Startup Control circuit with a high voltage enhancement mode MOSFET is included within the MC33363A. This circuitry allows for increased converter efficiency by eliminating the external startup resistor, and its associated power dissipation, commonly used in most off-line converters that utilize a UC3842 type of controller. Rectified ac line voltage is applied to the Startup Input, Pin 1. This causes the MOSFET to enhance and supply internal bias as well as charge current to the VCC bypass capacitor that connects from Pin 3 to ground. When VCC reaches the UVLO upper threshold of 15.2 V, the IC commences operation and the startup MOSFET is turned off. Operating bias is now derived from the auxiliary transformer winding, and all of the device power is efficiently converted down from the rectified ac line. The startup MOSFET will provide an initial peak current of 20 mA, Figure 10, which decreases rapidly as VCC and the die temperature rise. The steady state current will self limit in the range of 8.0 mA with VCC shorted to ground. The startup MOSFET is rated at a maximum of 400 V with VCC shorted to ground, and 500 V when charging a VCC capacitor of 1000 F or less. Regulator A low current 6.5 V regulated output is available for biasing the Error Amplifier and any additional control system circuitry. It is capable of up to 10 mA and has short-circuit protection. This output requires an external bypass capacitor of at least 1.0 F for stability. Thermal Shutdown and Package Internal thermal circuitry is provided to protect the Power Switch in the event that the maximum junction temperature is exceeded. When activated, typically at 155C, the Latch is forced into a `reset' state, disabling the Power Switch. The Latch is allowed to `set' when the Power Switch temperature falls below 145C. This feature is provided to prevent catastrophic failures from accidental device overheating. It is not intended to be used as a substitute for proper heatsinking. The MC33363A is contained in a heatsinkable plastic dual-in-line package in which the die is mounted on a special heat tab copper alloy lead frame. This tab consists of the four center ground pins that are specifically designed to improve thermal conduction from the die to the circuit board. Figures 15 and 16 show a simple and effective method of utilizing the printed circuit board medium as a heat dissipater by soldering these pins to an adequate area of copper foil. This permits the use of standard layout and mounting practices while having the ability to halve the junction to air thermal resistance. The examples are for a symmetrical layout on a single-sided board with two ounce per square foot of copper. Figure 22 shows a practical example of a printed circuit board layout that utilizes the copper foil as a heat dissipater. Note that a jumper was added to the layout from Pins 8 to 10 in order to enhance the copper area near the device for improved thermal conductivity. The application circuit requires two ounce copper foil in order to obtain 8.0 watts of continuous output power at room temperature.
MOTOROLA ANALOG IC DEVICE DATA
9
MC33363A
Figure 20. 15 W Off-Line Converter
F1 1.0 A D4 92 to 276 Vac Input D2 C1 47 R6 180 k 1.0 W D5 MUR 1100E 3 UVLO 14.5 V/ 9.5 V OVP 2.6 V 16 S Q PWM R LEB ILimit Thermal 9 270 A 4, 5, 12, 13 2.6 V EA 10 IC1 MC33363A R2 2.7 k 4 5 Driver C2 10 R4 5.1 k R3 1.0 k C6 47 pF R7 2.2 k 1.0 W D6 R5 MUR 39 120 D7 T1 MBR 1635 L1 5.0 H R8 220 R9 2.80 k C7 100 nF 1 C11 220 5.05 V/3.0 A DC Output
D3 1N4006 D1
C5 4.0 nF 1 Startup
Mirror C4 1.0 R1 13 k C3 1200 pF 7 Osc PWM Latch 8 6 Reg
C9 C10 330 330
11
C8 330
1 2
IC2 3 MOC 8103 IC3 TL431B 2
C12 1.0
R10 2.74 k
Figure 21. Converter Test Data
Test Conditions Results
Line Regulation Load Regulation
Vin = 92 Vac to 276 Vac, IO 3.0 A Vin = 115 Vac, IO = 0.75 A to 3.0 A Vin = 230 Vac, IO = 0.75 A to 3.0 A Vin = 115 Vac, IO = 3.0 A Vin = 230 Vac, IO = 3.0 A Vin = 115 Vac, IO = 3.0 A Vin = 230 Vac, IO = 3.0 A
= 1.0 mV = 5.0 mV = 5.0 mV Triangular = 2.0 mVpp, Spike = 32 mVpp Triangular = 2.0 mVpp, Spike = 34 mVpp 76.8%* 76.8%
Output Ripple
Efficiency
This data was taken with the components listed below mounted on the printed circuit board shown in Figure 22. * With MBR2535CTL, 78.8% efficiency. PCB layout modification is required to use this rectifier. For high efficiency and small circuit board size, the Sanyo Os-Con capacitors are recommended for C8, C9, C10 and C11. C8, C9, C10 = Sanyo Os-Con #6SA330M, 330 F 6.3 V. C11 = Sanyo Os-Con #10SA220M, 220 F 10 V. L1 = Coilcraft S5088-A, 5.0 H, 0.11 . T1 = Coilcraft U6875-A Primary: 77 turns of # 28 AWG, Pin 1 = start, Pin 8 = finish. Two layers 0.002 Mylar tape. Secondary: 5 turns of # 22 AWG, 2 strands bifiliar wound, Pin 5 = start, Pin 4 = finish. Two layers 0.002 Mylar tape. Auxiliary: 13 turns of # 28 AWG wound in center of bobbin, Pin 2 = start, Pin 7 = finish. Two layers 0.002 Mylar tape. Gap: 0.011 total for a primary inductance (LP) of 620 H. Core and Bobbin: Coilcraft PT1950, E187, 3F3 material.
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MOTOROLA ANALOG IC DEVICE DATA
MC33363A
Figure 22. Printed Circuit Board and Component Layout (Circuit of Figure 20) Caution! High Voltages
D1 D2 F1 IC1 L1 R1 R2
DC Output C4 C3 J1 R3 R3 IC2 C7 IC3 R10 R9 C12
C11
AC Line Input
R4 C2 D6 D3 D4 D5 R7 T1 C1 R6 R5
R8
C10
C9
D7 C5 C6 1 (Top View) 2.75" C8
MC33363A
2.25"
(Bottom View)
MOTOROLA ANALOG IC DEVICE DATA
11
MC33363A
OUTLINE DIMENSIONS
-A- T
16 9
DW SUFFIX PLASTIC PACKAGE CASE 751N-01 (SOP-16L) ISSUE O -B- P 0.010 (0.25)
M
B
M
1
8
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 (0.005) TOTAL IN EXCESS OF D DIMENSION AT MAXIMUM MATERIAL CONDITION. MILLIMETERS MIN MAX 10.15 10.45 7.40 7.60 2.35 2.65 0.35 0.49 0.50 0.90 1.27 BSC 0.25 0.32 0.10 0.25 0_ 7_ 10.05 10.55 0.25 0.75 2.54 BSC 3.81 BSC INCHES MIN MAX 0.400 0.411 0.292 0.299 0.093 0.104 0.014 0.019 0.020 0.035 0.050 BSC 0.010 0.012 0.004 0.009 0_ 7_ 0.395 0.415 0.010 0.029 0.100 BSC 0.150 BSC
J
13X
D
M
0.010 (0.25)
TA
S
B
S
F
C -T- S
9X SEATING PLANE
R X 45_
K G
M P SUFFIX PLASTIC PACKAGE CASE 648E-01 (DIP-16) ISSUE O
DIM A B C D F G J K M P R S T
-A- R
16 9
-B-
1 8
M P L F J -T-
SEATING PLANE
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 4. DIMENSION A AND B DOES NOT INCLUDE MOLD PROTRUSION. 5. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.25 (0.010). 6. ROUNDED CORNER OPTIONAL. DIM A B C D F G H J K L M P R S INCHES MIN MAX 0.740 0.760 0.245 0.260 0.145 0.175 0.015 0.021 0.050 0.070 0.100 BSC 0.050 BSC 0.008 0.015 0.120 0.140 0.295 0.305 0_ 10 _ 0.200 BSC 0.300 BSC 0.015 0.035 MILLIMETERS MIN MAX 18.80 19.30 6.23 6.60 3.69 4.44 0.39 0.53 1.27 1.77 2.54 BSC 1.27 BSC 0.21 0.38 3.05 3.55 7.50 7.74 0_ 10 _ 5.08 BSC 7.62 BSC 0.39 0.88
C S H G D 13 PL 0.25 (0.010)
M
K
TB
S
A
S
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MC33363A/D MOTOROLA ANALOG IC DEVICE DATA

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